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LM1893 Folha de dados(PDF) 11 Page - National Semiconductor (TI)

[Old version datasheet] Texas Instruments acquired National semiconductor.
Nome de Peças LM1893
Descrição Electrónicos  LM1893/LM2893 Carrier-Current Transceiver
Download  24 Pages
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Fabricante Electrônico  NSC [National Semiconductor (TI)]
Página de início  http://www.national.com
Logo NSC - National Semiconductor (TI)

LM1893 Folha de dados(HTML) 11 Page - National Semiconductor (TI)

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Component Selection (Continued)
power capability than standard avalanche diodes rated for
equal DC dissipation Metal oxide varistors have not proven
useful because of their inferior clamping coefficient and are
not recommended Specifications for an example minimum
diode are given in
Figure 13
Breakdown Voltage
44 – 49V
1mA
Maximum Leakage
1mA
40V
Capacitance
300 pF
BV
Maximum Clamp Voltage
645V
78A
Peak Non-Repetitive Pulse Power
10 kW for 1 ms
(REA Standard Exponential Pulse)
Surge Current
70A for 1120s
FIGURE 13 Key specifications for a recommended
transient suppressor ZT available from General
Semiconductor 2001 West Tenth Place Tempe AZ
85281 602 – 968-3101 part no SA40A
RT
RT acts as a voltage divider with ZT absorbing transient
energy that attempts to pull the Carrier Input pin above 44V
Make the resistor a carbon composition 14W When exper-
iments discharging CC charged to the peak-to-peak 620V
AC thru a 1X power line were carried out film resistors blew
open-circuit
DT
This Schottky diode is placed in parallel with the CCT chip’s
substrate diode to pass the majority of the current drawn
from ground when the Carrier Input or Carrier Output is
pulled below ground by a larger-than-twice-the supply-swing
on the tank Note that ZT is in parallel with the substrate
diode but is ineffective due to its high forward voltage drop
and high diffusion capacitance caused by its low forward
speed Tests proved that a 1N5818 kept a receive-path
functional with a 20X boost transmitter with a 71 transform-
er attempted to swing the receiver’s Carrier IO to g100V
(300 mA peak ground current in the receiver) Without DT
the receiver momentarily stops functioning at a 100 times
lower ground current
This diode is not needed if the Carrier IO never swings
below ground If your CCT systems all run on the same
regulated voltage with all matched transformers and turns
ratios it is not needed Otherwise it is
THE RECEIVER
The receiver and transmitter share components CC T1 CQ
RT ZT CO RO and peripheral supply and bias components
that are not in need of change for RX mode operation Val-
ues for the balance of the components are now found
Line-Frequency Rejection
To use the ultimate sensitivity of the device fully 110 dB of
115 V 60 Hz attenuation is required between the line and
the limiter amplifier output Using the circuit topology of
Fig-
ure 4 the combined attenuation of the CC T1 highpass the
tuned transformer and the bandpass filter attenuation of
the limiter amplifier give far more line rejection than the
above-stated minimum However if some other CCT line
coupling circuit is used line rejection will become important
to the system designer
Receiver input power supply rejection (PSRR) and common-
mode rejection (CMRR) are one-in-the-same using the sup-
ply-referenced signal input of
Figure 4 Ripple swings both
differential inputs of the Norton amp equally while the sin-
gle-ended input signal swings only the positive input Overall
PSRR consists of the input CMRR (set by the input stage
component matching) and the ripple-frequency attenuation
of the input amplifier bandpass response that passes carrier
frequency but stops low frequencies A typical 1% resistor
and 1 mV n-p-n mirror offsets give 26 dB of attenuation the
bandpass gives 54 dB 120 Hz attenuation for an overall 80
dB PSRR to allow tens of volts of ripple before impacting
ultimate sensitivity
CC
A value was chosen earlier Knowing T1’s secondary induc-
tance allows a check of LC line attenuation using
Figure 14
CL
The Norton input limiter amplifier has a bandpass filter for
enhanced receiver selectivity noise immunity and line fre-
quency rejection The nominal response curve for FO e 50
kHz is shown in
Figure 15 The 300 kHz pole is fixed The 50
kHz pole is set by CL’s value After CL is found the resulting
line frequency attenuation is found for the bandpass filter
Use
Figure 15 to find a CL value given for FO The approxi-
mate line frequency attenuation of the bandpass filter may
then be found in
Figure 16 Figure 15 returns a value for CL
33% larger than nominal giving a low frequency pole 33%
low to allow for component tolerances
TLH6750 – 15
FIGURE 14 The 60 Hz line rejection of the highpass
filter made up of CC and T1’s line-side winding
(neglecting capacitive coupling)
TLH6750 – 16
TLH6750 – 17
FIGURE 15 Given FO CL is found Also shown is the
input amplifier’s small signal amplitude response
11


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